Power conversion circuits

ABSTRACT

According to one embodiment, an AC power system includes a first AC/DC converter to be coupled to a direct current (DC) load and a multi-phase AC power supply. The system further includes a second AC/DC converter coupled in parallel with the first AC/DC converter via an interphase transformer to the DC load and the multi-phase AC power supply. The system further includes a controller coupled to the first and second AC/DC converters, where the controller is configured to generate a gate trigger signal for firing each of the rectifiers for the first and second AC/DC converters. During a first power cycle, a rectifier of the first AC/DC converter is fired at a firing angle advanced to a firing angle of a corresponding rectifier of the second DC/DC converter. During a second power cycle, the rectifier of the first AC/DC converter is fired at a firing angle lagging to a firing angle of the corresponding rectifier of the second AC/DC converter.

RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.12/890,311, filed Sep. 24, 2010, which is incorporated by referenceherein in its entirety.

FIELD OF THE INVENTION

The present invention relates generally to power conversiontechnologies. More particularly, this invention relates to powerconversion circuits.

BACKGROUND

Conversion of three-phase power has found many industrial applicationsthroughout this century. The proportion of converters connected to thesupply grid has reached high levels in the industrialized world. In itssimplest and most economical form, conversion of three-phase power isachieved by controlling the supply current in six steps per power supplycycle.

FIG. 1 is a schematic diagram illustrating a typical six-pulse AC to DCconverter. Referring to FIG. 1, a typical converter 100 includes athree-phase alternating current (AC) power supply 101 coupled to each ofthree inductors or alternate current (AC) reactors (or inductors)110-112, each connected to a pair of rectifiers 103 and 106, 104 and107, 105 and 108, respectively. Rectifiers 103-108 are controlled orswitched on by a controller or gate trigger circuit 102 to provide a DCoutput (DC voltage and DC current) to a DC load 109. Reactors 110-112(also referred to as AC chokes or inductors) and DC load 109 (which canbe considered a resistance in series with a DC reactor, sometimes incombination with a battery and/or capacitor) are combined to limit therate of rise of current and smooth the DC ripple current, respectively.Other electrical components, typically used for protection fromovervoltage and rate of change of voltage, protection, detection etchave been omitted from FIG. 1 for the purpose of simplicity and clarity.

A control voltage generated by controller 102 determines a delay anglealpha, α (also referred to as a firing angle), for rectifiers 103-108.The alpha delay angle is used to control the DC voltage and/or DCcurrent magnitude. Each rectifier switches once per power cycle (orperiod). For a constant control voltage signal each of rectifiers103-108 is triggered on at a constant delay angle of α degrees past itsanode-cathode voltage crossover point (in this example, α isapproximately 90 degrees as the load is considered mostly reactive),resulting in a corresponding phase shift between line voltage and linecurrent in each phase, and a change in DC voltage (or DC current).Voltages 113-115 are phased to neutral voltages, each being displaced by120 degrees from each other. Considering 113 as a reference 114 lags 113by 120 degrees, 115 lags 113 by 240 degrees. Voltage V1 is equal to thedifference between 113 and 115; voltage V2 is the difference between 114and 113; and voltage V3 is the difference between 115 and 114.

Waveform 201 of FIG. 2 shows the three-phase supply line to linevoltages V1, V2 and V3 connected to the AC terminals of the bridge. T0of V1, V2, V3 in waveform 201 is referred to as the anode-cathode zerovoltage crossover point for thyristors 103, 104 and 105, respectively.T0 of V1, V2, V3 in waveform 301 is referred to as the anode-cathodezero voltage crossover point for thyristors 106, 107 and 108,respectively. The delay time between anode-cathode voltage crossoverpoint (e.g. T0 in Waveform 201) and rectifier firing signal (e.g.waveform 203-205), typically measured in degrees, is known as the alphacontrol angle of the three-phase bridge. In steady state conditions thealpha control angle is substantially the same for each of rectifiers103-108. In waveform 201 this is approximately 90 degrees (shown). For aconstant control voltage from controller 102 the delay angle, or alpha,is substantially the same for each power cycle. As can be seen, eachrectifier begins conducting at the same delay angle to its correspondingsupply voltage, producing a three-phase AC current in reactors 110-112that is 90 degrees out of phase with the three-phase supply voltage.

Waveforms 201 and 301 of FIGS. 2 and 3 show the three-phase line to linesupply voltage for the converter. Waveform 202 shows the current throughrectifiers 103-105, and waveform 203-205 shows the gate trigger signalsgenerated by controller 102 to rectifiers 103-105. Waveform 302 showsthe current through rectifiers 106-108 (labeled) and waveforms 303-305show the gate trigger signals generated by controller 102 to rectifiers106-108. Gate trigger signals, for the positive and negative groups, areonly required to turn the rectifier on in a three-phase bridge. In thisexample, the rectifiers are considered to be thyristors. Hence the turnon of the next device in the series of the same group will switch offthe previous device in the series of the same group.

For example, in the positive group of thyristors 103-105, turn on ofdevice 104 will turn off device 103. Turn on of device 105 will turn offdevice 104 and so on. Using waveform 201 as a reference, two powercycles of duration “period 1” are shown in FIG. 2, where the delay angleof thyristors 103, 104 and 105 is substantially the same in each cycle.The rectifiers belonging to the positive group, 103-105, are switched inthe same sequence in each period. The current in each rectifier is phaseshifted by 90 degrees from its corresponding phase to neutral supplyvoltage. As can be seen in FIG. 3, using waveform 301 as a reference,the delay angle of rectifiers 106, 107 and 108 are substantially thesame in each cycle. Waveform 302 shows the rectifiers of the negativegroup of rectifiers 106-108 are switched in the same sequence in eachperiod. The current in each rectifier is phase shifted by 90 degreesfrom its corresponding phase to neutral supply voltage.

FIG. 4 shows the AC current in each phase of the bridge. The resultingAC current waveform, observed through chokes 110, 111, and 112 is aquasi-square waveform with a conduction angle of substantially 120degrees in the positive half cycle and substantially 120 degrees in thenegative half cycle, substantially regardless of the alpha controlangle. Waveform 321 shows the three-phase line to line voltage referenceV1, V2 and V3. The resultant line current waveforms flowing throughinductors 110-112 are shown in waveforms 322-324, respectively. The DCcurrent and voltage across load 109 is shown in waveform 325 and 326,respectively. As can be seen the DC current contains 6 “pulses” perperiod, or a ripple of 300 Hz (in this example the supply is 50 Hz). Thegate trigger signals to each rectifier, generated by controller 102, areshown in FIG. 5. Waveform 341 shows the three-phase line to line ACsupply voltage V1, V2, and V3. Waveforms 342-347 show the gate triggersignals to each rectifier 103-108 respectively, shown over a minimum offour cycles.

Each of the AC line current waveforms (322-324) contains in practice atleast 20% of fifth harmonic current (in addition to higher orderharmonics) which contributes to voltage distortion of the AC supply atthe point at which the converter is connected. Further, presence ofharmonics in the AC supply can cause misoperation, misfiring or shutdownof sensitive equipment connected to the same AC bus, overvoltage due toharmonic resonance with passive components connected to the network,etc. Various worldwide regulations, standards, and user specificationsrequire converter manufacturers to substantially reduce the harmoniccurrents generated by new equipment (i.e. IEEE 519).

There are various harmonic mitigation techniques that can be used. Inone conventional approach, a harmonic filter is utilized that is tunedto the frequency of the problematic harmonic on the network. A filterconnected at the terminals of the three-phase bridge provides a lowimpedance shunt pathway at the frequency of the harmonic targeted, buthigh impedance for all other frequencies, thereby preventing theharmonic travelling upstream to the AC supply network and affectingother users connected to the same supply. However, as harmonic currentsincrease with load, there is generally a need to switch filters indiscrete steps to compensate for changes in harmonic currents, and toavoid an adverse effect on the power factor seen by the supply networkdue to the inserted filter. Also, expensive and inefficient blockingreactors may be required to avoid filter overloading by harmonicsproduced elsewhere in the plant or in the supply network. Generally aplant fitted with filters requires preliminary studies to be made andcareful designs to be completed before installing new equipment. Filterscan reduce harmonics if properly designed, but can also amplifyharmonics when changes to the plant supply are made. Harmonic filtersare also a cost burden that a client must pay in addition to theoriginal purchase of electronic equipment in order to comply withstandards.

In another conventional approach, phase shifting of the AC supplyvoltage is used as a method to cancel harmonics. With this method, threeincoming phases are split into two groups of isolated three phases andphase shifted with respect to each other by 30 degrees. If theconverters equally share the load, the addition of their AC currents maycancel the fifth harmonic current. However, phase shifting of the ACsupply requires the use of one or more transformers. This substantiallyincreases the costs, operating losses, and equipment size and weight ofconverting equipment. A typical three-phase transformer typically costsand weighs more than the AC/DC converter that is connected to it.Despite the significant disadvantages associated with both of thesemethods, they remain the dominant techniques of alleviating harmonicdistortion in AC power conversion systems.

SUMMARY OF THE DESCRIPTION

According to one embodiment, an AC power system includes a first AC/DCconverter to be connected to a direct current (DC) load and amulti-phase AC power supply, the first AC/DC converter having multiplerectifiers. The system further includes a second AC/DC converter withits AC terminals connected in parallel with the first AC/DC converterand its DC terminals connected in parallel via an interphasetransformer. The load is connected between the midpoints (or center tap)of the interphase transformers. The second AC/DC converter has multiplerectifiers. The system further includes a controller coupled to thefirst and second AC/DC converters, where the controller is configured togenerate a gate trigger signal for firing each of the rectifiers for thefirst and second AC/DC converters. During a first power cycle, arectifier of the first AC/DC converter is fired at a firing angleadvanced to a firing angle of the corresponding rectifier of the secondDC/DC converter. During a second power cycle, the rectifier of the firstAC/DC converter is fired at a firing angle lagging to the firing angleof the corresponding rectifier of the second AC/DC converter.

Other features of the present invention will be apparent from theaccompanying drawings and from the detailed description which follows.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention is illustrated by way of example and notlimitation in the figures of the accompanying drawings in which likereferences indicate similar elements.

FIG. 1 is a schematic diagram illustrating a typical six-pulseconverter.

FIGS. 2-5 show certain signals of a typical six-pulse converter as shownin FIG. 1.

FIGS. 6A-6C are block diagrams illustrating a power conversion systemaccording to some embodiments of the invention.

FIGS. 7-8, 9A-9B, 10A-10B, and 11A-11C show certain switching waveformsof rectifier pairs of a power conversion system as shown in FIGS. 6A-6Caccording to some embodiments of the invention.

FIG. 11D is a schematic diagram illustrating a converter circuitaccording to another embodiment of the invention.

FIG. 12 is a schematic diagram illustrating a typical single-phaseconverter.

FIG. 13 is a diagram illustrating waveforms of various nodes for thecircuit shown in FIG. 12.

FIG. 14 is a schematic diagram illustrating a single-phase converteraccording to one embodiment.

FIGS. 15A and 15B are diagrams illustrating waveforms of certain nodesfor the circuit shown in FIG. 14.

FIG. 16 is a schematic diagram illustrating a single-phase converteraccording to another embodiment.

FIGS. 17A and 17B are diagrams illustrating waveforms of certain nodesfor the circuit shown in FIG. 16.

FIG. 18 is a schematic diagram illustrating a single-phase converteraccording to another embodiment.

FIGS. 19A-19C are diagrams illustrating waveforms of certain nodes forthe circuit shown in FIG. 18.

FIGS. 20A and 20B are schematic diagrams illustrating converter circuitsaccording to some embodiments of the invention.

FIG. 21 shows certain waveforms of a three-phase converter circuit asshown in FIG. 20A.

FIGS. 22A and 22B are schematic diagrams illustrating converter circuitsaccording to some embodiments of the invention.

FIGS. 23-27 show certain waveforms of a three-phase converter circuit asshown in FIG. 22A.

DETAILED DESCRIPTION

In the following description, numerous details are set forth to providea more thorough explanation of embodiments of the present invention. Itwill be apparent, however, to one skilled in the art, that embodimentsof the present invention may be practiced without these specificdetails. In other instances, well-known structures and devices are shownin block diagram form, rather than in detail, in order to avoidobscuring embodiments of the present invention.

Reference in the specification to “one embodiment” or “an embodiment”means that a particular feature, structure, or characteristic describedin connection with the embodiment is included in at least one embodimentof the invention. The appearances of the phrase “in one embodiment” invarious places in the specification do not necessarily all refer to thesame embodiment. Reference to a “power cycle”, also referred to as theperiod, refers to the time interval required for the AC supply voltageto complete one cycle at which point it repeats itself periodically; theperiod is defined as the inverse of the frequency, F, defined in Hz.Most utility networks operate at 50 or 60 Hz; however a network cantheoretically operate at any frequency, depending on the application.Reference to a “rectifier” for the purpose of this paper refers to athyristor. However, any electronic, power electronic, electronicallytriggered subcycle switching element can be substituted to the sameeffect.

Three-Phase Converter Embodiments

According to some embodiments, an improved arrangement is provided forharmonic reduction in AC power converters. In one embodiment, asymmetrical control of firing angles of multiple (e.g., two or more)parallel complementary switched AC power converters about an nominal (oraverage) control angle, alpha, can be used to increase the number ofpulse components provided by the converters, and to at least partlycancel harmonic currents generated by the converters, thus providing arelatively simple and effective technique for reducing harmonic currentstransmitted to the AC network.

In one embodiment, an AC power conversion system includes at least twoAC power converter (e.g., AC/DC converters) circuits connected inparallel to a multiphase AC power supply. Each converter circuitincludes at least six controllable rectifiers for passing respectivephases of the AC power supply in turn at a respective firing angle foreach circuit. Each converter circuit further includes a controller forsymmetrically controlling the respective rectifiers so that the firingangles for the respective rectifiers in each converter circuit aresubstantially identical but oppositely offset from a nominal controlangle (also referred to as a base or average angle). As a result, thenet (or combined) AC and DC current of the converter circuits has agreater number of component pulses than if either converter circuitoperated alone.

In addition, according to one embodiment the AC power conversion systemfurther includes two (or more in the case of higher order pulse systems)interphase transformers (IPTs) connected between two positive and twonegative DC terminals of each converter circuit. The IPT serves to limita circulation current in the DC terminals during the time that there isa difference in DC voltage between the DC nodes of the two bridges. TheIPT also provides a means to apply a 12 pulse ripple voltage to the DCload. DC reactors can be used in place of interphase transformers toperform the same task of circulating current limitation (this is oftennot the case due to the IPT being cheaper from an economical point ofview. Additionally, the DC reactors used for circulation currentlimitation may also affect current ripple and the response time of theconverter). The potential across the load is equal to the resultingaverage DC voltage between the positive and negative DC terminals.

In one embodiment, the AC power supply is a three-phase power supply andtwo converter circuits are utilized. The two converter circuits may besubstantially identical or similar. In a further embodiment, theconversion system provides a 12 pulse current. The firing angles aresubstantially the same but oppositely offset from a nominal controlangle by approximately 15° (e.g., Δα=)±15°. This value can be varied toadjust the cancellation of harmonic current components. A thyristor maybe used as an example of a rectifier.

The choices of a nominal control angle (e.g., the base firing angle α)can be selected and/or adjusted as required to provide the operation ofthe conversion system in rectifier (0<alpha<90), inverter(90<alpha<180), and/or reactive compensator (alpha ˜90 deg) modes.Embodiments of the invention also include conversion systems having agreater number of converter circuits which can be used together toprovide, for example, a 24 pulse current with further reduced harmoniccontent.

FIG. 6A is a block diagram illustrating an example of an AC powerconversion system according to one embodiment of the invention.Referring to FIG. 6A, AC power conversion system 400 includes, but isnot limited to, three-phase AC power supply 401, controller 402, AC/DCconverters 403-404, interphase transformers 405-406, and a DC load 407.Controller 402 is configured to provide gate control signals (e.g.,pulse signals to turn on the respective rectifiers) to one or morerectifiers of AC/DC converters 403-404. The positive DC terminals ofpower converter 403-404 are connected in parallel via interphasetransformer (or DC reactors) 405. The negative DC terminals of powerconverters 403-404 are connected in parallel via interphase transformer(or DC reactor) 406. Note that in this example, single controller 402 isused to control both converters 403-404. However, multiple controllersmay also be utilized to individually control converters 403-404.

Reference to “corresponding rectifier” throughout this application istaken to mean, in the case that multiple bridges that are substantiallysimilar or identical in an embodiment, the rectifier in an alternatebridge that is connected in the same position as the original bridge.Referring to FIG. 6B, for example, rectifier 527 is the correspondingrectifier of rectifier 521. Similarly, rectifier 521 can be referred toas the corresponding rectifier of rectifier 527. Similarly, Rectifier530 is the corresponding rectifier of rectifier 524. Similarly,rectifier 524 can also be referred to as the corresponding rectifier ofrectifier 530. And so on.

Three-phase electric power is a common method of AC electric powertransmission. It is a type of polyphase systems, and is the most commonmethod used by electric power distribution grids worldwide to distributepower. It is also used to power large motors and other large loads. Athree-phase system is generally more economical than others because ituses less conductor material to transmit electric power than equivalentsingle-phase or two-phase systems at the same voltage. In a three-phasesystem, three circuit conductors carry three alternating currents (ofthe same frequency) which reach their instantaneous peak values atdifferent times. Taking one conductor as the reference, the other twocurrents are delayed in time by one-third and two-thirds of one cycle ofthe electrical current. This delay between phases has the effect ofgiving constant power transfer over each cycle of the current, and alsomakes it possible to produce a rotating magnetic field in an electricmotor.

A rectifier is an electrical device that converts AC to DC, a processknown as rectification. Rectifiers have many uses including ascomponents of power supplies and as detectors of radio signals.Rectifiers may be made of solid state diodes, vacuum tube diodes,mercury arc valves, and other components. In one embodiment, a thyristoris used as an example of a rectifier. Turn on of the thyristor may beaccomplished by a “positive current” pulse between the gate and cathodeterminals. Turn off of a thyristor, in a line commutated three-phaseAC/DC converter, is achieved by reversing the current in the thyristor.This can be achieved by firing the next thyristor that shares a commoncathode (or anode) in sequence, setting up a circulating current betweenphases that reverses the current direction and turns off the device.Although a thyristor is used as an example of a rectifier through thisapplication, it will be appreciated that other types of controlledswitches can also be utilized.

Referring back to FIG. 6A, in one embodiment, each of converters 403-404includes six controllable rectifiers for passing respective phases ofthe AC power supply in turn at a respective firing angle for eachcircuit. Controller 402 is configured to provide control signals forsymmetrically controlling the respective rectifiers of converters 403and 404, such that during any power cycle the firing angles for therespective (or corresponding) rectifiers inside converters 403-404 aresubstantially equally but oppositely offset from a base angle.Additionally, interphase transformers (IPTs) are connected between thetwo positive and two negative DC terminals of each converter circuit.The IPT serves to limit the circulation current between the terminals ofeach bridge for the period of time that there is a difference in voltagebetween two terminals. It also serves to provide a 12 pulse ripplevoltage across the DC load. The load experiences the average DC voltageof converters 403 and 404. As a result, the net AC and DC currents ofthe converters 403-404 have a greater number of component pulses thanfor each of converters 403-404 operating alone.

In one embodiment, converters 403-404 may be substantially equal, andthe respective loads and their DC currents are substantially equal. Thefiring angles for the corresponding rectifiers in each converter may besubstantially equal but oppositely offset from a nominal delay angle (α)by, for example, 15° (e.g., Δα=)±15° in an alternated manner. Forexample, given a rectifier of a first AC/DC converter (e.g., converter403), a first firing angle of the rectifier may be (α+Δα) during a firstpower cycle (or period) and a second firing angle may be (α−Δα) during asecond power cycle. The next firing angle is configured back to (α+Δα)in the third power cycle, etc. For the corresponding rectifier of asecond or complementary AC/DC converter (e.g., converter 404), thecorresponding firing angle is (α−Δα) for the first power cycle and(α+Δα) for the second power cycle, and (α−Δα) for the third power cycleetc. The magnitude of the offset value (e.g., Δα) can be varied toadjust the cancellation of harmonic current components. Note thatalthough two AC/DC converters are described with respect to FIG. 6A,three or more converters may also be utilized in parallel for theobjective of increasing the number of pulses per power cycle (i.e. to18, 24 pulses etc), for example, a 18 pulse circuit as shown in FIG.11D.

FIG. 6B is a schematic diagram illustrating an AC power conversionsystem according to another embodiment of the invention. For example,system 500 may be implemented as part of system 400 of FIG. 6A. Forpurposes of illustration, certain reference numbers of components havingidentical or similar functionalities are retained from previous figuresherein. Referring to FIG. 6B, similar to system 400 of FIG. 6A, system500 includes, but not limited to, AC power supply 401 having respectivephase to neutral voltages 501-503, controller 402, AC/DC converters403-404, interphase transformers 405-406, and a DC load 407. Supplyvoltages 501, 502 and 503 are connected between phase and neutral (orground) and are phase displaced from one another. Given 501 is areference, 502 lags 501 by 120 degrees and 503 lags 501 by 240 degrees.For the purpose of illustration, line to line voltages are defined asV1, V2, and V3. V1 is defined as the difference in potential between ACnode voltage 501 and 503; V2 is defined as the difference in potentialbetween AC node voltage 502 and 501; V3 is defined as the difference inpotential between AC node voltage 503 and 502. Converter 403 includesrectifiers 521-526 and converter 404 includes rectifiers 527-532,respectively. In one embodiment, a thyristor can be used as an exampleof any of rectifiers 521-532. Controller 402 is configured to providegate control signals to rectifiers 521-532 of AC/DC converters 403-404.Interphase transformers 405-406 are connected between the two positiveand two negative DC terminals of each converter circuit 403-404.Alternatively, DC reactors may be connected in place of each IPT coil.The load 407 is connected between the midpoints (or center tap) of eachIPT.

Voltages 501-503 represent respective phases of a three-phase AC powersupply 401, for example, as supplied by an electrical power utility. Inthis example, converters 403-404 are connected in parallel tothree-phase AC power supply 401 and are paralleled through interphasetransformers 405-406 to DC load 407, which represents an inductance andresistance of the load in this example; however, the load can also be aDC source (battery) or an Inverter. Reactors 544-546, 547-549 and541-543 represent transformer, cabling and connection impedances and areconsidered to be of sizing typical to a three-phase AC transmissionnetwork. For example, the total series reactance is typicallyapproximately (or less than) 5% of the voltage drop at full currentrating of the supply.

Controller 402 (also referred to as a gate trigger unit) may beimplemented using analog circuitry or, more preferably, by using amicroprocessor or microcontroller (e.g., field programmable gate arraysor FPGAs) which can be more readily programmed or adjusted as requiredto control the firing of converters 403-404. For example, controller 402may include a machine-readable storage medium (e.g., memory) to storemachine executable instructions that have been programmed according toone or more predetermined algorithms and a processor or processing logicor signal generator to generate proper gate trigger signals havingproper firing angles for each of rectifiers 521-532 based on theprogrammed algorithms.

In this example, controller 402 may produce 12 gate trigger signals, onefor each of rectifiers 521-532. In this example, converter 403 includessix rectifiers 521-526 and requires six triggering pulses to driverectifiers 521-526 and converter 404 includes six rectifiers 527-532 andrequires another six gate triggering pulses to drive rectifiers 527-532.Converters 403-404 are also referred to as three-phase bridges.Rectifiers 521, 522 and 523 are referred to as the positive group ofrectifiers of converter 403. Rectifiers 527, 528 and 529 are referred toas the positive group of rectifiers of converter 404. Rectifiers 527,528 and 529 are considered corresponding rectifiers to 521 522 and 523respectively. Rectifiers 524, 525 and 526 are referred to as thenegative group of rectifiers of bridge 403. Rectifiers 530, 531 and 532are referred to as the negative group of rectifiers of bridge 404.Rectifiers 530, 531 and 532 are considered corresponding rectifiers to524, 525 and 526 respectively.

According to one embodiment, system 500 is controlled at a nominalcontrol angle α (e.g. approximately 90 degrees), therefore drawingsubstantially only reactive power from the AC supply 401 in thisexample. DC load 407 is considered mostly inductive. Rectifiers insideconverter circuits 403-404 are switched in a complementary fashion, atfiring angles which are substantially equally offset (offset, meaningadvanced or delayed, or added/subtracted) from the nominal control angleby an offset angle Δα.

For purpose of illustration, the firing sequence of the positive groupof rectifiers of bridges 403 and 404 and the negative group ofrectifiers are shown in FIGS. 7 and 8. FIG. 9 shows the AC current ineach converter 403 and 404 (the current through reactors 544-549) andthe total combined AC current of bridges 403 and 404 (the AC currentthrough reactors 541-543).

Referring to FIG. 7, waveform 701 is the three-phase line to linevoltage of the AC supply used as a reference by controller 402 toproduce signals 621, 622, 623, 627, 628, and 629 to fire positive grouprectifiers 521, 522, 523 and 527, 528, 529 respectively. T0 of V1, V2,and V3 in waveform 701 is considered the anode-cathode zero voltagecrossover point for positive group thyristors 521 and 527, 522 and 528,523 and 529, respectively. V1 is defined as the difference in potentialbetween AC node voltage 501 and 503. V2 is defined as the difference inpotential between AC node voltage 502 and 501. V3 is defined as thedifference in potential between AC node voltage 503 and 502. Waveform702 shows the instantaneous current through each positive grouprectifier 521, 522, and 523. Waveform 703 is the instantaneous currentthrough each corresponding positive group rectifier 527, 528, and 529shown over two power cycles. Waveform 704 shows the gate trigger signals621 and 627 generated by controller 402 to fire rectifiers 521 and 527.Waveform 705 shows the gate trigger signals 622 and 628 for rectifiers522 and 528. Waveform 706 shows the gate trigger signals 623 and 629 forrectifiers 523 and 529.

Referring to FIG. 8, waveform 801 is the three-phase reference voltageof the AC supply used as a reference by controller 402 to producesignals 624, 625, 626, 630, 631, and 632 to fire negative grouprectifiers 524, 525, 526 and 530, 531, 532 respectively. T0 of V1, V2,and V3 in waveform 801 is considered the anode-cathode zero voltagecrossover point for negative group thyristors 524 and 530, 525 and 531,526 and 532 respectively. Waveform 802 shows the instantaneous currentthrough each negative group rectifier 524, 525, and 526 and waveform 803is the instantaneous current through each corresponding negative grouprectifier 530, 531, and 532 shown over two power cycles. Waveform 804shows gate trigger signals 624 and 630 generated by controller 402 tofire rectifiers 524 and 530. Waveform 805 contains gate trigger signals625 and 631 for rectifiers 525 and 531. Waveform 806 contains gatetrigger signals 626 and 632 for rectifiers 526 and 532.

Referring to FIG. 9, waveform 901 is equivalent to waveform 701.Waveform 902 and 903 and 904 show the AC current through reactors 544,547, and 541 respectively. Waveform 905, 906, and 907 show the ACcurrent through reactors 545, 548, and 542 respectively. Waveform 908,909, and 910 show the AC current through reactors 546, 549, and 543respectively. Referring to FIG. 10A, waveform 1001 is equivalent towaveform 701. Waveforms 1002, 1003, 1004, 1005, 1006, and 1007 show gatetrigger signals, over 4 power cycles, of rectifiers 521 and 527, 526 and532, 522 and 528, 524 and 530, 523 and 529, and 525 and 531,respectively.

Referring back to FIG. 7, which contains the firing sequence for thepositive group of rectifiers in converters 403 and 404, the nominalalpha delay angle, α, for both bridges 403 and 404 is approximately 90degrees (shown as a continuous line). The nominal alpha control angle isthe delay, in degrees, between the anode-cathode zero voltage crossover(shown as T0 for each respective phase and rectifier) and the triggersignal generated by controller 402 for the relevant rectifier. Apositive voltage trigger signal voltage turns on rectifier 521,corresponding to an instantaneous rise of current through the device(waveform 702). All rectifiers 521-532 in this example are consideredline commutated devices (e.g. thyristors), meaning the process of turnoff is not gate controlled but controlled by the AC voltage of thesupply. Hence, no gate signals for turn off are shown (or required inpractice). Observing waveform 701 as a reference voltage, in the firstpower cycle (period 1), it can be seen that rectifier 521 is fired at analpha delay angle of (α−Δα).

In the second power cycle of waveform 701 (e.g. period 2), rectifier 521is fired at an alpha delay angle of (α+Δα). By the third cycle ofwaveform 701 (not fully shown), the firing pattern described repeatsitself. In each period the corresponding rectifier of bridge 404,rectifier 527, is fired in a complementary fashion to rectifier 521.That is in the first power cycle of waveform 701 (period 1) rectifier527 is fired at an alpha delay angle of (α+Δα). In the second powercycle of waveform 701 (period 2) rectifier 527 is fired at an alphadelay angle of (α−Δα). The third power cycle of waveform 701 (period 3)rectifier 527 is fired at an alpha delay angle of (α+Δα); by the thirdcycle the firing patter described repeats itself (hence it is onlypartly shown). The switching algorithm for any rectifier has duration oftwo power cycles before repeating itself. Waveform 704 shows the gatesignals 621 and 627 for corresponding rectifiers 521 and 527respectively in bridge 403 and 404 on the same axis to give the reader aclearer understanding of the symmetry of the firing signals tocorresponding rectifiers about a nominal delay angle, α, on a cycle percycle basis. Δα in this example is 15 degrees.

Additionally in FIG. 7, within each of bridges 403 and 404, theswitching order (i.e. the order that each rectifier belonging to thesame group is switched within a single power cycle) of each rectifier isshown. In the positive and negative rectifier group of each converter403 and 404, within a single power cycle, each rectifier is triggered atan opposite advance or delay angle (Δα) to the previous rectifier of thesame group as the sequence of switching progresses. In this example, apositive group of rectifiers of converter 403 includes rectifiers521-523 while a negative group of rectifiers of converter 403 includesrectifiers 524-526. A positive group of rectifiers of converter 404includes rectifiers 527-529, while the negative group of rectifiers ofconverter 404 includes rectifiers 530-532. Within the first power cycle(period 1) shown by waveform 701, waveform 704 (and 702) shows rectifier521 is switched at an angle of (α−Δα), waveform 705 (and 702) showsrectifier 522 is switched at an angle of (α+Δα), and waveform 706 (and702) shows rectifier 523 is switched at an angle of (α−Δα). Within asecond power cycle (e.g., period 2) of waveform 701, waveform 704 (and702) shows rectifier 521 is switched at an angle of (α+Δα), waveform 705(and 702) shows rectifier 522 is switched at an angle of (α−Δα), andwaveform 706 (and 702) shows rectifier 523 is switched at an angle of(α+Δα). In the third switching cycle (period 3) of 701 the switchingsequence repeats itself.

Similarly, within the first power cycle (e.g., period 1), rectifier 527is switched at an angle of (α+Δα), rectifier 528 is switched at an angleof (α−Δα), and rectifier 529 is switched at an angle of (α+Δα). Duringthe second power cycle, rectifier 527 is switched at an angle of (α−Δα),rectifier 528 is switched at an angle of (α+Δα), and rectifier 529 isswitched at an angle of (α−Δα).

Observing waveform 801 of FIG. 8, which contains the firing sequence ofthe negative group of rectifiers in converters 403 and 404, as areference voltage in the first power cycle (e.g., period 1), it can beseen that rectifier 524 is fired at an alpha delay angle of (α+Δα). Inthe second power cycle of waveform 801 (e.g., period 2), rectifier 524is fired at an alpha delay angle of (α−Δα). By the third cycle ofwaveform 801 (not fully shown) the firing pattern described repeatsitself. In each period, corresponding rectifier 530 is fired in acomplementary fashion to rectifier 524. In the first power cycle ofwaveform 801 (e.g., period 1), rectifier 530 is fired at an alpha delayangle of (α−Δα). In the second power cycle of waveform 801 (e.g., period2), rectifier 530 is fired at an alpha delay angle of (α+Δα). The thirdpower cycle of waveform 801 (e.g., period 3), rectifier 530 is fired atan alpha delay angle of (α−Δα); by the third cycle the firing patterdescribed repeats itself. The switching algorithm for any rectifier hasduration of two power cycles before repeating itself. Waveform 804 showsthe gate signals 624 and 630 for corresponding rectifiers 524 and 530respectively in bridge 403 and 404 on a cycle per cycle basis on thesame axis to give the reader a clearer understanding of the symmetry ofthe firing signals about a nominal delay angle, α, on a cycle per cyclebasis. Δα in this example is 15 degrees.

Additionally in FIG. 8, within each bridge 403 and 404, the switchingorder (i.e. the order that each rectifier belonging to the same group isswitched within a single power cycle) of each rectifier is shown. In thepositive and negative rectifier group of each converter 403 and 404,within a single power cycle, each rectifier is triggered at an oppositeadvance or delay angle (Δα) to the previous rectifier of the same groupas the sequence of switching progresses. In this example, the negativegroup of rectifiers of converter 403 includes rectifiers 524-526, and530-532 of converter 404. Within a first power cycle (e.g., period 1)shown by waveform 801, waveform 804 (and 802) shows rectifier 524 isswitched at an angle of (α+Δα), waveform 805 (and 802) shows rectifier525 is switched at an angle of (α−Δα), and waveform 806 (and 802) showsrectifier 526 is switched at an angle of (α+Δα). Within a second powercycle (e.g., period 2) of waveform 801, waveform 804 (and 802) showsrectifier 524 is switched at an angle of (α−Δα), waveform 805 (and 802)shows rectifier 525 is switched at an angle of (α+Δα), and waveform 806and 802 shows rectifier 526 is switched at an angle of (α−Δα). In thethird switching cycle (e.g., period 3) of 801 the switching sequencerepeats itself.

Similarly, during the first power cycle (e.g., period 1), rectifier 530is switched at an angle of (α−Δα), rectifier 531 is switched at an angleof (α+Δα), and rectifier 532 is switched at an angle of (α−Δα). Duringthe second power cycle (e.g., period 2), rectifier 530 is switched at anangle of (α+Δα), rectifier 531 is switched at an angle of (α−Δα), andrectifier 532 is switched at an angle of (α+Δα).

FIG. 9A shows the resulting AC current in the three-phase supply of eachbridge 403 and 404, i.e., the current through line reactors 544-546 and547-549, and also the total AC current in each reactor 541-543. Waveform901 is the three-phase supply voltage connected to the AC terminals ofthe bridge (equivalent to waveform 701). Waveform 902 is the addition(taking into account phase and magnitude and polarity) of the current inrectifiers 521 and 524. In the addition of each current, phase magnitudeand polarity of the current may be taken into account. For instance, inwaveform 802 the current waveform in rectifier 524 is shown as positive(as a thyristor can only conduct unidirectional). However, from theperspective of the AC supply network the current is considered negativein polarity, and is shown thus. Waveform 903 is the addition (takinginto account phase, magnitude and polarity) of the current in rectifiers527 and 530. Waveform 904 is the addition (taking into account phasemagnitude and polarity) of waveforms 902 and 903. As can be seen, the ACcurrent supplied by the network contains more “steps” and has a highernumber of pulses than a typical six pulse bridge (described in priorart). The total harmonic distortion of waveform 904 is reduced to abouthalf of that of a typical six pulse bridge (waveforms 322-324).Waveforms 905-907 represent currents of inductors 545, 548, and 542,respectively. Waveforms 908-910 represent currents of inductors 546,549, and 543, respectively. For an offset angle Δα of 15°, for example,the 12 pulse current is symmetrical and the fifth harmonic is reduced toabout 6% from about 20% in existing 6 pulse systems.

Referring to FIG. 10A, waveform 1002 shows the firing sequence forcorresponding rectifiers 521 of converter 403 and rectifier 527 ofconverter 404, where signal 621 represents gate trigger signal forrectifier 521 and signal 627 represents gate trigger signal forrectifier 527. As can be seen, rectifier 521 of converter 403 isalternatively fired at delay angle (α−Δα) and (α−Δα) over two powercycles of V1 before repeating the delay angle (in period 3). At the sametime rectifier 527 of converter 404 is fired in a complementary fashionwith delay angle of (α−Δα) and (α−Δα) over two power cycles beforerepeating the delay angle (e.g., in period 3).

Similarly, waveform 1003 shows the firing sequence for correspondingrectifiers 526 of converter 403 and rectifier 532 of converter 404,where signal 626 represents a gate trigger signal for rectifier 526 andsignal 632 represents a gate trigger signal for rectifier 532. As can beseen, rectifier 526 of converter 403 is alternatively fired at delayangle (α−Δα) and (α+Δα) over two power cycles of V3 before repeatingitself. Meanwhile, rectifier 532 of converter 404 is fired in acomplementary fashion with delay angle of (α−Δα) and (α−Δα) over twopower cycles before repeating itself.

Similarly, waveform 1004 shows the firing sequence for correspondingrectifiers 522 of converter 403 and rectifier 528 of converter 404,where signal 622 represents a gate trigger signal for rectifier 522 andsignal 628 represents a gate trigger signal for rectifier 528. As can beseen, rectifier 522 of converter 403 is alternatively fired at delayangle (α+Δα) and (α−Δα) over two power cycles of V2 before repeatingitself. Meanwhile, rectifier 528 of converter 404 is fired in acomplementary fashion with delay angle of (α−Δα) and (α+Δα) over twopower cycles before repeating itself.

Similarly, waveform 1005 shows the firing sequence for rectifier 524 ofconverter 403 and rectifier 530 of converter 404, where signal 624represents a gate trigger signal for rectifier 524 and signal 630represents a gate trigger signal for rectifier 530. As can be seen,rectifier 524 of converter 403 is alternatively fired at delay angle(α+Δα) and (α−Δα) over two power cycles of V1 before repeating itself.Meanwhile, rectifier 530 of converter 404 is fired in a complementaryfashion with delay angle of (α−Δα) and (α+Δα) over two power cyclesbefore repeating itself.

Similarly, waveform 1006 shows the firing sequence for correspondingrectifiers 523 of converter 403 and rectifier 529 of converter 404,where signal 623 represents a gate trigger signal for rectifier 523 andsignal 629 represents a gate trigger signal for rectifier 529. As can beseen, rectifier 523 of converter 403 is alternatively fired at delayangle (α−Δα) and (α+Δα) over two power cycles of V3 before repeatingitself. Meanwhile, rectifier 529 of converter 404 is fired in acomplementary fashion with delay angle of (α+Δα) and (α−Δα) over twopower cycles before repeating itself.

Similarly, waveform 1007 shows the firing sequence for correspondingrectifiers 525 of converter 403 and rectifier 531 of converter 404,where signal 625 represents a gate trigger signal for rectifier 525 andsignal 631 represents a gate trigger signal for rectifier 531. As can beseen, rectifier 525 of converter 403 is alternatively fired at delayangle (α−Δα) and (α+Δα) over two power cycles of V2 before repeatingitself. Meanwhile rectifier 531 of converter 404 is fired in acomplementary fashion with delay angle of (α+Δα) and (α−Δα) over twopower cycles before repeating itself.

In other embodiments the offset angle, Δα, for the positive group ofrectifiers of each of bridges 403 and 404 may be reversed in polaritycompared to what has been described above. In other words, a triggersignal having a firing angle of (α−Δα) applied to any of rectifiers521-523 and 527-529 as shown in FIG. 10A may be replaced with a triggersignal having a corresponding firing angle of (α+Δα), andcorrespondingly any trigger signal having a firing angle of (α+Δα) forrectifiers 521-523 and 527-529 may be replaced with a trigger signalhaving a firing angle of (α−Δα). The total resulting AC current throughreactors 541-543 will be substantially the same (see e.g., waveforms904, 907, and 910).

Similarly, in other embodiments, the offset angle, Δα, for the negativegroup of rectifiers of each of bridges 403 and 404 may be reversed inpolarity compared to what has been described above. In other words, atrigger signal having a firing angle of (α−Δα) applied to any ofrectifiers 524-526 and 530-532 as shown in FIG. 10A may be replaced witha trigger signal having a corresponding firing angle of (α+Δα), andcorrespondingly any trigger signal firing angle of (α+Δα) for rectifiers524-526 and 530-532 may be replaced with a trigger signal firing angleof (α−Δα). The total resulting AC current through reactors 541-543 willbe substantially the same (waveforms 904, 907, 910).

For example, FIG. 10B illustrates a converter circuit having a differentpolarity of Δα in the negative group of rectifiers of bridges 403 and404. The positive group of trigger signals, i.e., waveforms 1009, 1011,and 1013 are substantially similar or identical to waveforms 1002, 1004,and 1006, respectively. The trigger signals in waveforms 1010, 1012, and1014 are oppositely offset in polarity from the nominal delay angle tothe trigger signals in waveforms 1003, 1005, and 1007, respectively.FIG. 9B shows the resulting AC current waveforms for the switchingpattern of FIG. 10B. As can be seen, the AC current waveforms of 914,917, and 920 are substantially the same as 904, 907, and 910.

In a further embodiment, the switching sequence frequency may berepeated every four (or more) cycles instead of every two cycles withouta substantial effect to the AC current through reactors 541-543. Thiswould require a rectifier to be triggered in advance (or delay) two (ormore) times in succession before being triggered in delay (or advance)another two times (or more) in succession. The resulting AC currentwaveforms in FIG. 9A, 904, 907, and 910, would remain unchanged, howeverthe IPTs 405 and 406 would be required to increase in size by two (ormore) times to cope with the lower AC voltage frequency applied acrossits terminals.

FIG. 11A is a diagram representing an enlarged waveform which mayrepresent any one of waveforms 704-706 of FIG. 7, waveforms 804-806 ofFIG. 8, waveforms 1002-1007 of FIG. 10A, and waveforms 1009-1014 of FIG.10B. For example, considering the circuit of FIG. 6B and considering thepositive group of rectifiers: signal 680 may represent any one ofsignals 621, 628, and 623, while signal 690 may represent any one ofsignals 627, 622, and 629 which are counterpart signals to signals 621,628, and 623, respectively. Alternatively, signal 680 may represent anyone of signals 627, 622, and 629, while signal 690 may represent any oneof signals 621, 628, and 623, which are counterpart signals to signals627, 622, and 629, respectively.

Similarly, considering the circuit of FIG. 6B and the negative group ofrectifiers: signal 680 may represent any one of signals 630, 625, and632 while signal 690 may represent any one of signals 624, 631, and 626which are counterpart signals to signals 630, 625, and 632.Alternatively, signal 680 may represent any one of signals 624, 631, and626 while signal 690 may represent any one of signals 630, 625, and 632,which are counterpart signals to signals 624, 631, and 626,respectively.

For an embodiment, the AC supply current passing through reactors541-543 remains substantially the same for each trio of rectifierschosen (from the positive or negative groups) to represent signal 680and 690 of FIG. 11B, once the rules of assignment described above arefollowed. The assignment of signals 608 and 609 of FIG. 11A torespective rectifiers in the positive group of converters 403 and 404 isnot influenced by the assignment of signals 608 and 609 of FIG. 11A torespective rectifiers in the negative group of converters 403 and 404,as AC current in the power supply through reactors 541-543 remainsunaffected. Similarly, according to one embodiment, the assignment ofsignals 608 and 609 of FIG. 11A to respective rectifiers in the negativegroup of converters 403 and 404 is not influenced by the assignment ofsignals 608 and 609 of FIG. 11A to respective rectifiers in the positivegroup of converters 403 and 404, as the AC current in the supply throughreactors 541-543 remains unaffected.

For example, in FIG. 10A, triggering signals 630, 625, and 632 can beconsidered to represent signal 680, and triggering signals 624, 631, and626 can be considered to represent signal 690 from FIG. 11A. FIG. 9Ashows the current in AC reactors 541-549 for this sequence of rectifiertriggering signals. In FIG. 10B, triggering signals 624, 631, and 626represent signal 680 and triggering signals 630, 625, and 632 representsignal 690 from FIG. 11A. FIG. 9B shows the current in the AC reactors541-549 for this sequence of rectifier triggering signals. In both FIGS.10A and 10B, the positive group of rectifiers has not changed theirsequence with respect to V1, V2, and V3. As can be seen in FIGS. 9A and9B, there is a change in the AC current waveforms at the terminals ofeach bridge in reactors 544-549, however, the resulting (added) ACcurrents in 541-543 remain unchanged.

According to one embodiment, an AC power conversion system includes afirst AC/DC converter to be coupled to a direct current (DC) load and amulti-phase AC power supply, the first AC/DC converter having multiplerectifiers. The system further includes a second AC/DC converter coupledin parallel with the first AC/DC converter via an interphase transformerto the DC load and the multi-phase AC power supply, the second AC/DCconverter having multiple rectifiers. The system further includes acontroller coupled to the first and second AC/DC converters, where thecontroller is configured to generate a gate trigger signal for firingeach of the rectifiers for the first and second AC/DC converters. Duringa first power cycle, a rectifier of the first AC/DC converter is firedat a firing angle advanced to a firing angle of a correspondingrectifier of the second DC/DC converter. During a second power cycle,the rectifier of the first AC/DC converter is fired at a firing anglelagging to a firing angle of the corresponding rectifier of the secondAC/DC converter.

According to another embodiment, an AC power conversion system includesat least two AC power converter circuits for coupling respective loadsin parallel to a multi-phase AC power supply, each AC power convertercircuit containing multiple rectifiers (e.g., six rectifiers) forpassing respective phases of the AC power supply in turn at respectivefiring angles. The system further includes a controller coupled to theat least two AC power converter circuits for symmetrically controllingthe rectifiers of the at least two AC power converter circuits, suchthat the firing angles for the corresponding rectifiers in the at leasttwo AC power converter circuits are substantially equally, butoppositely offset from a nominal control angle. A net current of the atleast two AC power converter circuits has a greater number of componentpulses than an individual AC power converter operating alone. The systemfurther includes two interphase transformers (IPTs) that are connectedbetween the two positive and two negative DC terminals of each convertercircuit. The potential between the midpoint (or center tap) of IPTs isthe average of the instantaneous DC voltage between the two positive andtwo negative rectifier groups in each converter bridge. The load isconnected between the two midpoints of the IPT. As a result, the netcurrent of the converters has a greater number of component pulses thanfor each of converters operating alone.

According to a further embodiment, an AC power conversion systemincludes a first AC/DC converter to be coupled to a direct current (DC)load and a multi-phase AC power supply, the first AC/DC converter havinga first rectifier, a second rectifier, a third rectifier, a fourthrectifier, a fifth rectifier, and a sixth rectifier, forming a firstthree-phase bridge. The system further includes a second AC/DC convertercoupled with the first AC/DC converter via an interphase transformer(IPT) to the DC load and the multi-phase AC power supply, the secondAC/DC converter having a seventh rectifier, a eighth rectifier, a ninthrectifier, a tenth rectifier, a eleventh rectifier, and a twelfthrectifier, forming a second three-phase bridge. The first and secondthree-phase bridges are coupled to each other in parallel. The systemfurther includes a controller coupled to the first and second AC/DCconverters, where the controller is configured to generate a gatetrigger signal for firing each of the rectifiers for the first andsecond AC/DC converters.

In one embodiment, during a first power cycle the first rectifier of thefirst AC/DC converter is fired at a firing angle advanced to a firingangle of the seventh rectifier of the second DC/DC converter, and duringa second power cycle, the first rectifier of the first AC/DC converteris fired at a firing angle lagging to a firing angle of the seventhrectifier of the second AC/DC converter. In addition, during the firstpower cycle, the second rectifier of the first AC/DC converter is firedat a firing angle lagging to a firing angle of the eighth rectifier ofthe second DC/DC converter, and during the second power cycle, thesecond rectifier of the first AC/DC converter is fired at a firing angleadvanced to a firing angle of the eighth rectifier of the second AC/DCconverter.

In one embodiment, during the first power cycle, the third rectifier ofthe first AC/DC converter is fired at a firing angle advanced to afiring angle of the ninth rectifier of the second DC/DC converter, andduring the second power cycle, the third rectifier of the first AC/DCconverter is fired at a firing angle lagging to a firing angle of theninth rectifier of the second AC/DC converter. In addition, during thefirst power cycle, the fourth rectifier of the first AC/DC converter isfired at a firing angle lagging to a firing angle of the tenth rectifierof the second DC/DC converter, and during the second power cycle, thefourth rectifier of the first AC/DC converter is fired at a firing angleadvanced to a firing angle of the tenth rectifier of the second AC/DCconverter.

In one embodiment, during the first power cycle, the fifth rectifier ofthe first AC/DC converter is fired at a firing angle lagging to a firingangle of the eleventh rectifier of the second DC/DC converter, andduring the second power cycle, the fifth rectifier of the first AC/DCconverter is fired at a firing angle advanced to a firing angle of theeleventh rectifier of the second AC/DC converter. In addition, duringthe first power cycle, the sixth rectifier of the first AC/DC converteris fired at a firing angle advanced to a firing angle of the twelfthrectifier of the second DC/DC converter, and during the second powercycle, the sixth rectifier of the first AC/DC converter is fired at afiring angle lagging to a firing angle of the twelfth rectifier of thesecond AC/DC converter.

Referring back to FIG. 6B, as converters 403-404 are coupled on the DCload 407 via interphase transformers 405-406 and converters 403-404 aresymmetrically controlled. DC reactors limiting the rate of rise ofcirculating current between the positive set of rectifiers and thenegative set of rectifiers can be used in place of the IPTs. Thedecision in practice of whether to use DC reactors or IPTs wouldnormally be an economic one influenced by the application and systemparameters such as AC supply frequency, AC supply voltage, and rawmaterial costs, and so on. The purpose of the IPT (or DC reactor) is tolimit the circulating current between positive and negative sets ofrectifiers in each bridge. The net current provided by converters403-404 includes more component pulses than a produced if each of theconverters 403-404 operated alone on the three-phase supply. As aresult, at least some higher order harmonics in the net current arepartly cancelled.

Referring to FIG. 6B, using a neutral (or earth) as a reference for thepositive and negative voltages of each bridge (Vp1, Vp2, Vn1, Vn2), thepositive terminal of load 407, designated ‘+’, is equal at all times toone half the addition of Vp1 and Vp2 (waveform 1210).

Using the neutral (or earth) point as a reference the negative terminalof load 407, designated ‘−’ is equal at all times to one half theaddition of Vn1 and Vn2 (waveform 1212). The resulting voltage acrossthe load is the difference between plus (+) and minus (−), or thedifference between waveforms 1210 and 1212. This is represented bywaveform 1213, as can be seen this is a low amplitude voltage with a 12pulse (600 Hz) ripple.

FIG. 11B shows various DC voltage waveforms for the conversion systemshown in FIG. 6B according to one embodiment. Waveform 1202 containsgraphs of the cathode (Vp1, Vp2) DC voltage of converter circuit403-404, and waveform 1204 contains graphs of the anode (Vn1, Vn2) DCvoltage of converter circuit 403-404, when an offset Δα is used.Waveforms 1203 and 1205 represent the voltages across the windings ofthe interphase transformers 405-406, respectively. One purpose of theinterphase transformers 405-406 is to limit the circulating currentbetween the positive and negative rectifier groups, respectively. Acirculating current may be formed when there is an instantaneous voltagedifference between the nodes Vp1 and Vp2, or Vn1 and Vn2. Specifically,at the instant when one rectifier of the positive group of 403 is firedin advance of a rectifier in positive group of converter 404 (e.g.rectifier 521 is fired in advance to rectifier 527), a voltage mayappear between nodes Vp1 and Vp2 equal to substantially theinstantaneous difference between node voltage 501 and 503 at the time offiring.

Additionally, when one rectifier of the negative group of 403 is firedin advance (or delay) of a rectifier in the negative group of converter404 (e.g. rectifier 524 is fired in advance to rectifier 530), a voltagemay appear between nodes Vn1 and Vn2 equal substantially to thedifference between node voltage 501 and 503. The magnitude of theinstantaneous voltage is dependent on the circuit parameters such as ACvoltage, supply impedance, average alpha delay angle etc. The duration,in degrees, of the voltage difference between nodes Vp1 and Vp2 issubstantially equal to twice the alpha offset angle, or 2Δα. Themagnitude and duration of the voltage difference affect the size andcost of the interphase transformer or DC reactor. For low supplyfrequency applications, an IPT may be a cheaper alternative to limitingthe circulating current. For high frequency applications, a DC reactormay be more economical at limiting the circulating current. However, thelogic behind this is largely influenced by the cost of raw materials atany one time and is therefore subject to change according to respectiveglobal market conditions. The result is a low amplitude voltage with 12pulse ripple on the DC load 407, as shown in waveform 1206.

In a further embodiment the IPTs may be inserted in series withindividual thyristors, as shown in FIG. 6C. While the electricalperformance of the bridge remains substantially identical to that ofFIG. 6B described above, in some applications it can be advantageous forassembly sizing to insert the windings of the IPT in a low currentrectifier path rather than the high current path of the DC terminals.Additionally, the IPT coils can be carefully physically arranged on themagnetic core to provide the necessary amount of series (leakage)reactance to, in combination with the RC snubbers across each rectifier(not shown for simplicity), protect the rectifiers at turn off. Thismeans the separate line reactors 541-549 are substantially not requiredto be included in the circuit for protection of the rectifiers,therefore in some applications offering further energy and cost savings.

While the example described and illustrated in this application uses aΔα of approximately 15°, Δα can be arbitrarily selected for the mostappropriate operations. In one embodiment, the operation in the regionof the 15° is generally referred to as, for a Δα of 15°, the fifthharmonic is reduced to about 6%, while also reducing other higher orderharmonic components. In addition, a Δα equal to 15° produces a symmetric12 pulse current in the supply. If a Δα of approximately 18° is chosen,the fifth harmonic is substantially reduced or eliminated.

A 12 pulse ripple is desirable as frequency dependent loads, such as theDC inductor can be reduced in capacity to approximately a quarter ofthat used in systems which provide symmetric 6 pulse operation. Further,the response time of the system is halved from approximately 3.33milliseconds in a classical (typical) six pulse thyristor bridge(FIG. 1) to approximately 1.67 milliseconds in the case of Δα=15degrees. The dynamic response is also significantly faster than in aclassical six pulse bridge due to the lower necessary DC impedance. Thevalue of Δα can be set at a fixed value for a given application, orperiodically adjusted. As an example, a control algorithm can beimplemented on a microprocessor or controller to adjust α and/or Δα asrequired.

In one embodiment, the interphase transformers 405-406 are much smallerand more efficient than the three-phase transformers used in existingphase shifting applications as described above. Phase shiftingtransformers are triple wound, galvanically isolated magnetic componentsthat are expensive, bulky and inefficient. Also, inrush currents offully rated phase shifting transformers are avoided. Each of interphasetransformers 405-406 has two windings, and is rated for the differencein voltage between two converters 403-404 and operates at approximately1.5 times the supply frequency. The interphase transformers 405-406 maybe gapped to prevent saturation due to a difference in DC currents.Alternatively, the firing angles of the positive or negative group ofrectifiers can be adjusted slightly to ensure equal DC currents flowthrough the windings of the interphase transformers 405-406.

According to a further embodiment, two or more converter circuits of thetype described above can be paralleled to produce waveforms having morecomponent pulses. For example, the addition of a converter circuit canbe arranged to produce 18 pulse current waveforms, providing even lowersupply harmonic distortion (see FIG. 11D). An additional pair ofconverter circuits can be arranged to produce 24 pulse AC currentwaveforms, and so on.

As indicated by the various cases, the described method of symmetricalphase control is applicable through the full range of converter phaseangle control, making it suitable for conversion, inversion, or reactiveconverter operations. The described conversion system avoids the needfor splitting and phase shifting the power supply using bulkytransformers. The control of gating pulses allows harmonic currentcancellation, and thus a significantly decreased level of harmonicdistortion drawn from the power supply.

In another embodiment, as shown in FIG. 20A, the DC terminals of eachbridge are coupled to each other only magnetically through the IPTcoils, and there is no physical conductive connection between the DCterminals. In this embodiment, there are now two pairs of DC terminalsfor which to connect two separate loads. The load can be a battery or aresistance, similar to FIGS. 6A, 6B, and 6C. The advantage of thisembodiment is that two separate IPTs 405 and 406 shown in FIG. 6A havebeen reduced to a single IPT of substantially the same rating as IPT 405and 406 combined. The firing sequence of the controller 402 of FIGS. 20Aand 20B is identical to those detailed in FIGS. 7-10.

FIG. 21 shows various DC voltage and current waveforms of each bridge403 and 404 according to one embodiment. Waveform 2102 contains graphsof the DC voltage of converter circuit 403-404. The DC voltage ofconverter 403 is defined as the difference between Vp1 and Vn1. The DCvoltage of converter 404 is defined as the difference between Vp2 andVn2. Waveform 2103 represents the voltage across one winding of theinterphase transformer 408. Due to a phase shift between the two bridges403 and 404 (the phase shift reverses polarity every 2 power cycles, butthe magnitude remains the same) there is a transmission of voltage fromone bridge to another via the IPT. This results in a 12 pulse DC ripplevoltage across each load 407 a and 407 b, as shown in waveform 2104 and2105 respectively. Waveform 2106 and 2107 show the DC current through DCload 407 a and 407 b, respectively.

Another embodiment is shown in FIG. 20B. FIG. 20B shows a circuit withall elements and firing signals identical to FIG. 20A but with the IPT408 removed. The AC current waveforms through reactors 541-543 aresubstantially the same as for the system of FIG. 20A, however, therequired size of the DC reactor 407 a and 407 b is larger in order toobtain the same harmonic distortion in the AC supply currents throughreactors 541-543. This is because the removal of the IPT 407 hasrendered the DC voltage ripple across each load 407 a and b to beessentially 6 pulses. The phase shift between converters 403 and 404still provides harmonic cancellation.

Fixed Displacement Firing Embodiments

According to some embodiments, the rectifiers in bridges 403 and 404 ofFIG. 20 can be controlled using a different technique to the oneillustrated in FIGS. 7 to 11. FIG. 22A is a schematic diagram similar toFIG. 20 but with a different controller 415. In one embodiment, thecontroller 415 triggers rectifiers at a delay angle from theirrespective anode-cathode zero crossing according to the group in whichthey belong inside bridge 403 and 404. Each converter circuit iscontrolled by controller 415 for symmetrically controlling therespective rectifier groups so that the firing angles for the respectiverectifier groups in each converter circuit are substantially equally butoppositely offset from a nominal control angle (also referred to as abase or average angle). The firing signals from controller 415 are fixedfor each group of rectifiers, and do not change within each period, orfrom period to period. As a result, the net (or combined) AC and DCcurrent of the converter circuits has a greater number of componentpulses than if either converter circuit operated alone.

Referring to FIG. 22A, converters 403-404 are referred to as three-phasebridges. Rectifiers 521, 522, and 523 are referred to as the positivegroup of rectifiers of converter 403. Rectifiers 527, 528, and 529 arereferred to as the positive group of rectifiers of converter 404.Rectifiers 524, 525, and 526 are referred to as the negative group ofrectifiers of bridge 403. Rectifiers 530, 531, and 532 are referred toas the negative group of rectifiers of bridge 404. According to oneembodiment, FIG. 22A is controlled at a nominal control angle α (in thecase illustrated in this paper alpha is approximately 90 degrees),therefore drawing substantially only reactive power from the AC supply401 in this example. The DC loads, 407 a and 407 b, is considered mostlyinductive. Rectifier groups inside converter circuits 403-404 areswitched in a complementary fashion, at firing angles which aresubstantially equally offset (offset, meaning advanced or delayed, oradded/subtracted) from the nominal control angle by an offset angle Δα.Firing signal delay or advance from controller 415 to each rectifiergroup are constant and are not cyclic (i.e. they do not change frompower cycle to power cycle).

In one embodiment, the positive rectifier group of converter 403containing rectifiers 521, 522, and 523 is fired, in every power cycle,at an advanced offset angle Δα to a nominal delay angle α. Conversely,the positive rectifier group of converter 404 containing rectifiers 527,528, and 529 is fired, in each power cycle, at a delayed offset angle Δαto a nominal delay angle α. Additionally, the negative rectifier groupof converter 403 containing rectifiers 524, 525, and 526 is fired, inevery power cycle, at an delayed offset angle Δα to a nominal delayangle α. Conversely, the negative rectifier group of converter 404containing rectifiers 530, 531, and 532 is fired, in each power cycle,at an advanced offset angle Δα to a nominal delay angle α.

Within a converter, the positive and negative groups of rectifiers mayhave opposing offset angle polarity. If the positive group of converter403 is chosen to be fired at an offset angle that is advanced from thenominal delay angle then negative group of rectifiers of converter 403may be fired at an offset angle that is delayed from the nominal delayangle α.

Between converters 403 and 404, the positive and negative groups ofrectifiers may have opposing offset angle polarity. If the positivegroup of converter 403 is chosen to be fired at an offset angle that isadvanced from the nominal delay angle, then the positive group ofconverter 404 must be fired in a complementary fashion at an offsetangle that is delayed from the nominal delay angle α.

Referring to FIGS. 23 and 24. For purpose of illustration, the firingsequence of the positive group of rectifiers of bridges 403 and 404(FIG. 23) and the negative group of rectifiers (FIG. 24) is shown inseparate figures. FIG. 25A shows the AC current in each converter 403and 404 (the current through reactors 544-549) and the total combined ACcurrent of bridges 403 and 404 (the AC current through reactors541-543).

Waveform 2301 is the three-phase line to line voltage of the AC supplyused as a reference by controller 415 to produce signals 621-623 and627-629 to fire positive group rectifiers 521-523 and 527-529,respectively. T0 of V1, V2, and V3 in waveform 2301 is referred to asthe anode-cathode zero voltage crossover point for positive groupthyristors 521-527, 522-528, and 523-529, respectively. V1 is defined asthe difference in potential between AC node voltage 501 and 503. V2 isdefined as the difference in potential between AC node voltage 502 and501. V3 is defined as the difference in potential between AC nodevoltage 503 and 502. Waveform 2302 shows the instantaneous currentthrough each of rectifiers 521, 522, and 523, and waveform 2303 is theinstantaneous current through each rectifier 527, 528, and 529, shownover two power cycles. Waveform 2304 shows the gate trigger signals 621and 627 generated by controller 415 to fire rectifiers 521 and 527.Waveform 2305 shows the gate trigger signals 622 and 628 for rectifiers522 and 528. Waveform 2306 shows the gate trigger signals 623 and 629for rectifiers 523 and 529.

Waveform 2401 is the three-phase reference voltage of the AC supply usedas a reference by controller 415 to produce signals 624-626 and 630-632to fire negative group rectifiers 524-526 and 530-532, respectively. T0of V1, V2, V3 in waveform 2401 is considered the anode-cathode zerovoltage crossover point for negative group thyristors 524-530, 525-531,and 526-532, respectively. Waveform 2402 shows the instantaneous currentthrough each of rectifiers 524-526 and waveform 2403 is theinstantaneous current through each of rectifiers 530-532, shown over twopower cycles. Waveform 2404 shows gate trigger signals 624 and 630generated by controller 415 to fire rectifiers 524 and 530. Waveform2405 contains gate trigger signals 625 and 631 for rectifiers 525 and531. Waveform 2406 contains gate trigger signals 626 and 632 forrectifiers 526 and 532.

Waveform 2501 of FIG. 25A is similar to waveform 2301. Referring to FIG.22A, waveform 2502, 2503, and 2504 show the AC current through reactors544, 547, and 541, respectively. Waveform 2505, 2506, and 2507 show theAC current through reactors 545, 548, and 542, respectively. Waveform2508, 2509, and 2510 show the AC current through reactors 546, 549, and543, respectively.

Waveform 2601 of FIG. 26 is similar to waveform 2301. Referring to FIG.26, waveforms 2602-2607 show gate trigger signals, over 4 power cycles,of rectifiers 521 and 527, 526 and 532, 522 and 528, 524 and 530, 523and 529, and 525 and 531, respectively.

FIG. 27 shows the voltage waveforms and DC current on the DC side of thebridges 403 and 404. Waveform 2702 shows the DC voltage of each bridge(i.e. Vp1-Vn1, and Vp2-Vn2) on the same axis. Waveform 2703 shows thevoltage across one IPT coil. Waveform 2704 and 2705 are substantiallythe same, showing the resulting 12 pulse, low amplitude voltage rippleacross each load 407 a and 407 b. Waveform 2706 and 2707 show the DCcurrent in each bridge.

Referring back to FIG. 23, which contains the firing sequence for thepositive group of rectifiers in converters 403 and 404, the nominalalpha delay angle cc, for both bridges 403 and 404 is 90 degrees (shownas a continuous line). The nominal alpha control angle is the delay, indegrees, between the anode-cathode zero voltage crossover (shown as T0for each respective phase and rectifier) and the trigger signalgenerated by controller 415 for the relevant rectifier. A positivevoltage trigger signal voltage will turn on rectifier 521, correspondingto an instantaneous rise of current through the device (waveform 2302).All rectifiers 521-532 in this example are considered line commutateddevices, (e.g. thyristors) meaning the process of turn off is not gatecontrolled but controlled by the AC voltage of the supply. Hence, nogate signals for turn off are shown (or required in practice). Observingwaveform 2301 as a reference voltage, it can be seen that rectifier 521is fired at an alpha delay angle of (α−Δα) in each period. In eachperiod, rectifier 527 is fired in a complementary fashion to rectifier521, while rectifier 527 is fired at an alpha delay angle of (α−Δα).Waveform 2304 shows the gate signals 621 and 627 for correspondingrectifiers 521 and 527 respectively in bridge 403 and 404 on the sameaxis to give the reader a clearer understanding of the unchangedsymmetry of the firing signals about a nominal delay angle, α, on acycle per cycle basis. Δα in this example is approximately 15 degrees.

Additionally in FIG. 23, within each of bridges 403 and 404, theswitching order (i.e. the order that each rectifier belonging to thesame group is switched within a single power cycle) of each rectifier isshown. In the positive and negative rectifier group of each ofconverters 403 and 404, within a single power cycle, each rectifierconducts for substantially 120 degrees before the next rectifier in thesame group (positive or negative) is triggered. Triggering of the nextrectifier in succession may switch off the previous rectifier in thesame group. In this example, there are three rectifiers in each groupeach conducting for approximately 120 degrees of a power cycle, addingto approximately 360 degrees for a full power cycle. As can be seen inFIG. 23, a rectifier of any group conducts once per power cycle,triggered at an offset angle to the nominal delay angle that is the samein polarity each power cycle.

It is useful to note that the polarity of the offset angle Δα chosen forpositive and negative groups in each bridge 403 and 404 has nosubstantial effect on the line current supplied by the AC supply 401. Itmay be only essential to ensure the polarity of the offset angle Δα isopposite between respective positive rectifier groups of 403 and 404 andnegative rectifier groups of 403 and 404. Also, it is important that theoffset angle Δα of the positive and negative rectifier groups within abridge 403 or 404 may be opposite in polarity.

Single-Phase Converter Embodiments

According to some embodiments, the techniques described above can alsobe applied to single-phase converters. FIG. 12 is a schematic diagramillustrating a conventional single-phase converter. Referring to FIG.12, the converter contains four switches and one AC power supply. Eachswitch conducts current for 180 degrees out of 360 degrees in a powercycle. During the positive half cycle of the AC power sine wave,thyristors 1 and 2 are fired (substantially simultaneously) at an angleof alpha delay past the zero crossing of their anode cathode voltage.Alpha can have a range of 0 to 90 degrees in the case where the bridgeis acting as a rectifier and 90 to 180 degrees in the case where theconverter is acting as an inverter.

During the negative half cycle of the AC power sine wave thyristors 3and 4 are fired (simultaneously) at an angle of delay past the zerocrossing of their anode to cathode voltage. The resulting currentwaveform is shown in FIG. 13. At all times, irrespective of alpha angleof delay, each thyristor conducts current for 180 degrees, or half apower cycle. The resulting AC line current, drawn from the AC powersupply, is shown in FIG. 13. Note that at no instant is the AC currentequal to zero (amps) for any substantial length of time. In other wordsthe AC current is rigorously bipolar, crossing zero with a (relatively)sharp rate of change of current, at the instant of firing the positive(thyristor 1 and 2) or negative (thyristor 3 and 4) group of thyristors.The AC line current is rich in current harmonics, beginning from thethird order (3 times the fundamental frequency) upwards. The totalharmonic current distortion is approximately 45% (at least,theoretically), with the third harmonic reaching up to 33% offundamental current. Harmonic filters are the predominant technique usedfor reducing the THID to acceptable levels in an AC network (adherenceto IEEE 519).

According to some embodiments, multiple converters are utilized,connected in parallel, and fired in a sequence to achieve a reduction inharmonic currents that would otherwise normally be generated in priorart. FIG. 14 is a schematic diagram illustrating a single-phaseconverter according to one embodiment of the invention. Referring toFIG. 14, two single-phase bridges are connected in parallel. Note thatmore bridges can also be connected in parallel to achieve furtherharmonic reduction. The positive groups of thyristors, in both bridges,are considered to be thyristor 1 and 2. These thyristors fire, at analpha delay angle, only during the positive half of the power frequencysine wave. Alpha, as described before, can range, theoretically,approximately between 0 to 180 degrees delay from the anode-cathodevoltage crossing.

In one embodiment, thyristor 1 and 2 are fired at the same time (as canbe seen their gate signals are tied) to provide a path for the positivehalf cycle of current. The negative groups of thyristors, in bothbridges, are considered to be thyristor 3 and 4. They fire, at an alphadelay angle, only during the negative half of the power frequency sinewave. Thyristor 3 and 4, in a single bridge, are fired at the same time.As can be observed in FIGS. 14 and 15A-15B, their gate signals are tiedwithin a bridge. The AC current harmonics are reduced by firing thegroup of thyristors (positive or negative) from the pair of bridgessymmetrically about an average alpha delay angle.

In a single power cycle, according to one embodiment, the same group ineach bridge may be fired symmetrically about an average common alphadelay angle. In other words, in the first power cycle, the positivegroup of thyristors of bridge A are fired at delay (α+Δα) and thepositive group of thyristors of bridge B are fired at delay (α−Δα). Inthe second power cycle, the delay angles are reversed between the twogroups of thyristors. In the second power cycle the positive group ofthyristors of bridge A are fired at delay (α−Δα) and the positive groupof thyristors of bridge B are fired at delay (α+Δα). In the third powercycle the positive group of thyristors of bridge A are fired at delay(α+Δα) and the positive group of thyristors of bridge B are fired atdelay (α−Δα). The third power cycle firing delay is exactly the same asthe first power cycle, so the pattern can be considered to repeat itselfat this point. The combined AC current of the two bridges results in aquasi-square waveform. The conduction time of the waveform is dependenton the Δα chosen. For a Δα=15 degrees a conduction time of 120 degreesresults. The total harmonic distortion of such a waveform is reduced to(theoretically) around 30%, as shown in FIGS. 15A and 15B.

Further, the Δα chosen for the positive group of thyristors is allowedto be different (greater or less) than the Δα chosen for the negativegroup. FIG. 16 is a schematic diagram illustrating a converter accordingto another embodiment of the invention. This will result in an AC quasisquare current waveform that is advanced (or delayed) in the positivehalf cycle of the power cycle, and delayed (or advance) in the negativehalf cycle of the power cycle, as shown in FIGS. 17A and 17B.

By combining multiple pairs or bridges with this arrangement of firing,according to one embodiment, the combined AC current distortion can bereduced further. FIG. 18 is a schematic diagram illustrating a converteraccording to another embodiment of the invention. Referring to FIG. 18,in this example, there are four bridges (or two pairs) and the THDreduces to about 14%, as shown in FIGS. 19A-19C. It will be appreciatedthat more paralleled bridges may reduce the current distortion further.

In the foregoing specification, embodiments of the invention have beendescribed with reference to specific exemplary embodiments thereof. Itwill be evident that various modifications may be made thereto withoutdeparting from the broader spirit and scope of the invention as setforth in the following claims. The specification and drawings are,accordingly, to be regarded in an illustrative sense rather than arestrictive sense.

What is claimed is:
 1. An alternating current (AC) power conversionsystem, comprising: a first AC/DC converter to be coupled to a firstdirect current (DC) load and an AC power supply, the first AC/DCconverter having a first positive group of rectifiers and a firstnegative group of rectifiers; a second AC/DC converter to be coupled toa second DC load and the AC power supply, the second AC/DC converterhaving a second positive group of rectifiers and a second negative groupof rectifiers; an interphase transformer having a first winding and asecond winding mutually wounded onto a common core, wherein the firstwinding is coupled in series with the first DC load and an output of thefirst AC/DC converter, and wherein the second winding is coupled inseries with the second DC load and the second AC/DC converter; and acontroller coupled to the first and second AC/DC converters, wherein thecontroller is configured to generate a gate trigger signal for firingeach of the rectifiers of the first and second AC/DC converters, whereinthe first positive group of rectifiers of the first AC/DC converter isfired at a firing angle advanced to a nominal firing angle, wherein thesecond positive group of rectifiers of the second AC/DC is fired at afiring angle lagging from the nominal firing angle during a firstswitching cycle, wherein the first negative group of rectifiers of thefirst AC/DC converter is fired at a firing angle lagging to the nominalfiring angle, and wherein the second negative group of rectifiers of thesecond AC/DC is fired at a firing angle advanced from the nominal firingangle during the first switching cycle.
 2. The system of claim 1,wherein the corresponding rectifiers of the first and second AC/DCconverters are fired at firing angles with an advanced (α−Δα) or delayed(α+Δα) offset (Δα) to the nominal firing angle (α) in each switchingcycle.
 3. The system of claim 2, wherein firing angles of rectifiers ofthe first and second AC/DC converters remain the same over a pluralityof switching cycles.
 4. The system of claim 2, wherein the offset (Δα)is configured to be 15 degrees.
 5. The system of claim 2, wherein thenominal firing angle (α) is configured to be 90 degrees.
 6. The systemof claim 2, wherein corresponding groups of rectifiers of the first andsecond AC/DC converters are fired with a firing angle that is offset,but opposite, to the nominal firing angle.
 7. The system of claim 6,wherein the first positive group of rectifiers are fired at a firingangle of (α−Δα) and the second positive group of rectifiers are fired ata firing angle of (α+Δα), and wherein the first negative group ofrectifiers are fired at a firing angle of (α+Δα) and the second negativegroup of rectifiers are fired at a firing angle of (α−Δα).
 8. The systemof claim 6, wherein the first positive group of rectifiers are fired ata firing angle of (α+Δα) and the second positive group of rectifiers arefired at a firing angle of (α−Δα), and wherein the first negative groupof rectifiers are fired at a firing angle of (α−Δα) and the secondnegative group of rectifiers are fired at a firing angle of (α+Δα). 9.The system of claim 1, wherein the first negative group of rectifiers ofthe first AC/DC converter is fired at a firing angle lagging from thenominal firing angle, and wherein the second negative group ofrectifiers of the second AC/DC is fired at a firing angle advanced tothe nominal firing angle during the first switching cycle.
 10. Thesystem of claim 1, wherein the first positive group of rectifiers of thefirst AC/DC converter is fired at a firing angle lagging from thenominal firing angle, and wherein the second positive group ofrectifiers of the second AC/DC is fired at a firing angle advanced tothe nominal firing angle during a second switching cycle.
 11. The systemof claim 10, wherein the first negative group of rectifiers of the firstAC/DC converter is fired at a firing angle advanced to the nominalfiring angle, and wherein the second negative group of rectifiers of thesecond AC/DC is fired at a firing angle lagging from the nominal firingangle during the second switching cycle.
 12. An alternating current (AC)power conversion system, comprising: a first AC/DC converter to becoupled to a direct current (DC) load and an AC power supply, the firstAC/DC converter having a first positive group of rectifiers and a firstnegative group of rectifiers; a second AC/DC converter to be coupled tothe DC load and the AC power supply, the second AC/DC converter having asecond positive group of rectifiers and a second negative group ofrectifiers; a first interphase transformer (IPT) having a first windingand a second winding mutually wounded onto a first common core; a secondIPT having a third winding and a fourth winding mutually wounded onto asecond common core, wherein the first IPT and the second IPT couple thefirst AC/DC converter and the second AC/DC converter in parallel to theDC load; a controller coupled to the first and second AC/DC converters,wherein the controller is configured to generate a gate trigger signalfor firing each of the rectifiers of the first and second AC/DCconverters, wherein the first positive group of rectifiers of the firstAC/DC converter is fired at a firing angle advanced to a nominal firingangle, wherein the second positive group of rectifiers of the secondAC/DC is fired at a firing angle lagging from the nominal firing angleduring a first switching cycle, wherein the first negative group ofrectifiers of the first AC/DC converter is fired at a firing anglelagging to the nominal firing angle, and wherein the second negativegroup of rectifiers of the second AC/DC is fired at a firing angleadvanced from the nominal firing angle during the first switching cycle.13. The system of claim 12, wherein the first winding and the secondwinding of the first IPT form a first end terminal, a second endterminal, and a first center tap, wherein the third winding and thefourth winding of the second IPT form a third end terminal, a fourth endterminal, and a second center tap, wherein the first end terminal of thefirst IPT is coupled to a positive output terminal of the first AC/DCconverter, wherein the second end terminal of the first IPT is coupledto a positive output terminal of the second AC/DC converter, wherein thefirst center tap of the first IPT is coupled to a positive terminal ofthe DC load.
 14. The system of claim 13, wherein the third end terminalof the second IPT is coupled to a negative output terminal of the firstAC/DC converter, wherein the fourth end terminal of the second IPT iscoupled to a negative output terminal of the second AC/DC converter,wherein the second center tap of the second IPT is coupled to a negativeterminal of the DC load.
 15. The system of claim 12, wherein thecorresponding rectifiers of the first and second AC/DC converters arefired at firing angles with an advanced (α−Δα) or delayed (α+Δα) offset(Doc) to the nominal firing angle (α) in each switching cycle.
 16. Thesystem of claim 15, wherein firing angles of rectifiers of the first andsecond AC/DC converters remain the same over a plurality of switchingcycles.
 17. The system of claim 15, wherein the offset (Δα) isconfigured to be 15 degrees.
 18. The system of claim 15, wherein thenominal firing angle (α) is configured to be 90 degrees.
 19. The systemof claim 15, wherein corresponding groups of rectifiers of the first andsecond AC/DC converters are fired with a firing angle that is offset,but opposite, to the nominal firing angle.
 20. The system of claim 19,wherein the first positive group of rectifiers are fired at a firingangle of (α−Δα) and the second positive group of rectifiers are fired ata firing angle of (α+Δα), and wherein the first negative group ofrectifiers are fired at a firing angle of (α+Δα) and the second negativegroup of rectifiers are fired at a firing angle of (α−Δα).